Using preamble portion having irregular carrier spacing for frequency synchronization

ABSTRACT

In one embodiment, an apparatus includes: a radio frequency (RF) front end circuit to receive and downconvert a RF signal to a second frequency signal, the RF signal comprising an orthogonal frequency division multiplexing (OFDM) transmission; a digitizer coupled to the RF front end circuit to digitize the second frequency signal to a digital signal; and a baseband processor coupled to the digitizer to process the digital signal. The baseband circuit comprises a first circuit having a first plurality of correlators having an irregular comb structure, each of the first plurality of correlators associated with a carrier frequency offset and to calculate a first correlation on a first portion of a preamble of the OFDM transmission.

The present application is a continuation of U.S. patent applicationSer. No. 17/536,732, filed on Nov. 29, 2021 in the name of FredericPirot entitled “Using Preamble Portion Having Irregular Carrier SpacingFor Frequency Synchronization,” which claims the benefit of U.S.Provisional Application No. 63/250,533, filed on Sep. 30, 2021, in thename of Frederic Pirot entitled “System, Method And Apparatus ForIrregular Pilot Comb For Robust Preamble Carrier OffsetSynchronization,” U.S. Provisional Application No. 63/250,542, filed onSep. 30, 2021, in the name of Frederic Pirot entitled “System, MethodAnd Apparatus For Full Complex Random Pilot Sequence For OrthogonalFrequency Division Multiplexing Symbol Generation” and U.S. ProvisionalApplication No. 63/250,555, filed on Sep. 30, 2021, in the name ofFrederic Pirot entitled “System, Method And Apparatus For FrequencyHopped Successive Orthogonal Frequency Division Multiplexing Symbols ForRobust Preamble Detection And Synchronization,” the content of which ishereby incorporated by reference.

BACKGROUND

In some wireless communication systems, an orthogonal frequency divisionmultiplexing (OFDM) waveform is used. Such waveform enables using thefull available bandwidth with a nearly flat spectrum, and it is possibleto remove inter-symbol interference, thanks to an added cyclic prefix,insertion of pilots among data is easy and can be used for simplesynchronization/equalization.

With OFDM signals, especially in burst systems at very lowsignal-to-noise ratio (SNR), coarse synchronization on carrier frequencyoffset (CFO) of the incoming signal is sometimes badly estimated due tothe regular frequency shape of the preamble symbols. Thus with OFDMsignals at very low SNR, synchronization on a symbol within a precisetime window is difficult to achieve. To do so, a detectable repetitionof the signal is typically used. This will work down to a few decibels(dB) of SNR. Another technique is to introduce a detectable disruptionon the signal. Classical disruptions like complex-phase inversion of aknown signal sequence can typically work down to SNR on the order of 0dB. However, for much lower SNR (e.g., −10 dB down to −20 dB), thesetechniques may be ineffective.

Another disadvantage of OFDM is its high Peak-to-Average Power Ratio(PAPR). This power ratio is an important aspect of the transmissionbecause it impacts the maximum transmit power that can be achieved witha full transmission equipment. In modern standards, preambles aresometimes designed with specific care for power consumption vstransmission power. However in some standards, pilots are only modulatedby binary sequences, and, based on this usually the chosen pilotsequence is the one among all the sequences that, matching otherconditions, has the smallest PAPR.

SUMMARY OF THE INVENTION

In one aspect, an apparatus includes: a radio frequency (RF) front endcircuit to receive and downconvert a RF signal to a second frequencysignal, the RF signal comprising an orthogonal frequency divisionmultiplexing (OFDM) transmission; a digitizer coupled to the RF frontend circuit to digitize the second frequency signal to a digital signal;and a baseband processor coupled to the digitizer to process the digitalsignal. The baseband circuit comprises a first circuit having a firstplurality of correlators having an irregular comb structure, each of thefirst plurality of correlators associated with a carrier frequencyoffset and to calculate a first correlation on a first portion of apreamble of the OFDM transmission.

In an example, the apparatus is to receive the first portion of thepreamble having a first plurality of symbols, each of the firstplurality of symbols having a plurality of carriers, wherein a firstsubset of the plurality of carriers have non-zero values. The apparatusmay receive the plurality of carriers comprising N carriers, where N-Mof the N carriers are the first subset having the non-zero values. Atleast some of the N-M carriers have irregular carrier spacing. Theirregular comb structure of the first plurality of correlators maycorrespond to the irregular carrier spacing of the at least some N-Mcarriers. The apparatus may receive the non-zero values formed by anon-N-ary complex number sequence.

In an example, the apparatus further comprises a fast Fourier transform(FFT) engine to receive the OFDM transmission and to output theplurality of symbols each having the plurality of carriers in afrequency domain. The apparatus may receive the first plurality ofsymbols comprising identical symbols.

The first circuit may comprise a carrier frequency offset circuit todetermine a carrier frequency offset based on the first correlationcalculated by the first plurality of correlators. The baseband circuitfurther comprises a second circuit having a second plurality ofcorrelators, each of the second plurality of correlators associated witha time-phase, the second portion of the preamble having at least onefrequency disruption, each of the second plurality of correlators tocalculate a second correlation on the second portion of the preamble.The apparatus may further include a non-volatile memory to store a firstconfiguration setting to define the irregular comb structure of thefirst plurality of correlators.

In another aspect, a method comprises: receiving an OFDM transmission ina receiver; and performing a frequency estimation on a first preambleportion of the OFDM transmission using a plurality of correlators of thereceiver, the first preamble portion formed of a plurality of symbols,each of the plurality of symbols having N-M non-zero carriers, where atleast some of the N-M non-zero carriers are irregularly spaced.

In an example, the method further comprises using the plurality ofcorrelators comprising a set of irregularly spaced comb correlators toperform the frequency estimation, where the set of irregularly spacedcomb correlators corresponds to the irregular spacing of the at leastsome N-M non-zero carriers. The method may further comprise performing acoarse frequency estimation on the first preamble portion using the setof irregularly spaced comb correlators. The method may further includeperforming a fine frequency estimation on the first preamble portionbased on the coarse frequency estimation and using the set ofirregularly spaced comb correlators. The method may further includeconfiguring the receiver for receipt of a data portion of the OFDMtransmission based at least in part on the fine frequency estimation.Configuring the receiver may include adjusting a frequency of a mixingsignal used to downconvert a RF signal of the OFDM transmission to alower frequency signal.

In yet another aspect, a system comprises: an antenna to receive andtransmit RF signals; and an integrated circuit coupled to the antenna.The integrated circuit may include: a transmitter to generate andtransmit an OFDM transmission, the transmitter comprising a preamblegeneration circuit to generate a first portion of a preamble of the OFDMtransmission having a first plurality of symbols, each of the firstplurality of symbols having a plurality of carriers, where a firstsubset of the plurality of carriers have non-zero values, at least someof the first subset of the plurality of carriers having irregularcarrier spacing.

In an example, the integrated circuit comprises a first storage to storean identification of the first subset of the plurality of carriershaving the non-zero values. The transmitter may transmit the firstportion of the preamble having the irregular carrier spacing to optimizecoarse frequency processing at a receiver of the OFDM transmission.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a flow diagram of a method in accordance with an embodiment.

FIG. 2 is a graphical illustration of a preamble of an OFDMcommunication in accordance with an embodiment.

FIG. 3 is a block diagram of a transmitter in accordance with anembodiment.

FIG. 4 is a block diagram of a receiver in accordance with anembodiment.

FIG. 5 is a graphical illustration of a representative irregular pilotcomb of a first preamble portion and corresponding irregular combstructures of a plurality of correlators of a receiver.

FIG. 6 is a graphical illustration of an example preamble including afirst portion having a plurality of symbols followed by a second portionalso having a plurality of symbols.

FIG. 7 is a graphical illustration of another example preamble includinga first portion followed by a second portion.

FIG. 8 is a graphical illustration of yet another example preambleincluding a first portion followed by a second portion.

FIG. 9 is a graphical illustration of a still further example preambleincluding a first portion followed by a second portion.

FIG. 10 is a graphical illustration of an example preamble for afrequency mix scenario with a shift sequence having continuous carriersfor disruption.

FIG. 11 is a block diagram of a representative integrated circuit thatincorporates an embodiment.

FIG. 12 is a high level diagram of a network in accordance with anembodiment.

DETAILED DESCRIPTION

In various embodiments, a preamble structure of a packet, frame or otherblock of information of a wireless communication may be provided toenable more efficient detection of an OFDM transmission. To this end, apreamble may be provided that can be detected easily, even with apotentially high carrier frequency shift. The preamble may include afirst portion that has a relatively simple waveform structure. Thisfirst preamble portion may be long enough to perform detection (DET),coarse frequency (CF) and fine frequency (FF) algorithms (which meansthat these algorithms may be configured to be insensitive to the framestart position in time). Next, to detect the beginning of the packet, asecond portion of the preamble may be provided with a disruption, e.g.,a frequency disruption from symbol to symbol over time. As embodimentsmay operate in a very noisy environment, this preamble portion may havea relatively long disruption, to realize an efficient coarse time (CT)algorithm. This same second preamble portion and/or an optional thirdpreamble portion (which may be formed of a complete fully known OFDMsymbol) may be used to provide information to a fine time algorithm(FT).

In radio burst communication standards, a burst is typically constructedwith a preamble, signalization, and a payload. The preamble is used for:detection of the data burst; coarse (approximative) synchronization intime; coarse (approximative) synchronization in frequency; fine(precise) synchronization in time; and fine (precise) synchronization infrequency. In a given receiver, all of these algorithms may be executedconcurrently or successively, based at least in part as a function ofpreamble architecture and design choices. Signalization is used fortransmission of modulation parameters, and the payload contains theuseful data.

In an OFDM system, coarse synchronization in time involves finding thereceived OFDM symbol start with a precision of a few incoming samples(generally defined as a fraction of the OFDM symbol size). Coarsesynchronization in frequency involves finding the frequency offset ofthe incoming signal with a precision of 1 OFDM carrier spacing. Finesynchronization in time involves finding the received OFDM symbol startwith a precision of an incoming sample. Fine synchronization infrequency involves finding the residual frequency offset of the incomingsignal with a precision of a fraction of 1 OFDM carrier spacing(typically 10% or below).

A perfect illustration of this frame structure is in a Wireless SmartUbiquitous Network (Wi-SUN) network in which OFDM is used in accordancewith the IEEE 802.15.4-2020 specification. In this OFDM radio burststandard, a packet is constructed according to this specification. Inthis specification, for a given packet there is 1 preamble; 1 PHY Header(PHR) for signalization; and 1 Payload (PSDU). The preamble is dividedin 2 parts: a Short Training Field (STF); and a Long Training Field(LTF). In this preamble, the LTF is usually used for fine timing/finefrequency and other operations. The STF is usually used for detection,coarse frequency, fine frequency, and coarse timing. This STF itself canbe divided in 2 parts: a long, stable part, used for: detection; coarsefrequency; and fine frequency; and a short (complex-phase disruptivepart) at the end of the STF that is used for coarse timing. The spectrumof the preamble (OFDM representation of the symbol in the frequencydomain) has a frequency structure that is based on a subset of regularlyspaced carriers modulated by a binary sequence. However, thisWi-SUN-based implementation may not work well in high noiseenvironments.

In embodiments, various aspects of a preamble structure can be selectedto enable receipt and processing of incoming OFDM communications atlonger ranges and lower signal levels than available in a Wi-SUNimplementation. More particularly, embodiments may be used to enablereception of OFDM communications at sensitivity levels down toapproximately −130 dB. Thus embodiments may be used to enable receptionof wireless communications at lower sensitivity levels. Moreparticularly, embodiments may be used to receive signals that are lowerthan a noise level, while still detecting and demodulating the signals.

To this end, a first preamble portion may be provided with irregularcarrier spacing, to enable better correlations to occur usingcorrelators in a receiver that are tuned to this irregular carrierspacing. That is, these correlators also may have an irregular combstructure to correspond or match this irregular carrier spacing. In thisway, these correlators may process incoming preambles to result in abetter auto-correlation vs cross-correlation ratio and, in case ofstrong noise, limit the probability of a bad coarse CFO estimation dueto correlation ambiguity between multiple different CFO correlatorcandidates.

Also in embodiments, better CFO processing may be realized where thisfirst preamble portion is generated using a non-N-ary (e.g., non-binary)sequence of complex numbers, rather than a pilot sequence based on amodulated binary sequence as is used in Wi-SUN. Still further, thevalues used for this non-N-ary sequence of complex numbers may beselected to realize transmission having a minimum possible PAPR. Togenerate such a sequence, the criteria could be, for example pilots'position within the OFDM symbol (typically a regular pilot comb); andall pilots be transmitted with the same power. With this example, theliberty degree to generate minimum PAPR sequence would then be thecomplex-phase of the complex numbers.

Of course, pilots with different transmission power may be used and PAPRmay be minimized by optimizing the complex-phase and the module of eachcarrier. In any case, the complex values for the pilots may be chosenfor their PAPR optimization properties, with no other sequenceconsideration such as specific link to a binary sequence.

Still further in various embodiments, a series of frequency disruptionsor carrier shifts may be provided in a second portion of a preamble(e.g., from one OFDM symbol to the next during this second preambleportion). With this arrangement, there may be successive disruptions,both on the time and frequency components of the signal. With anappropriate detection algorithm, symbol start may be detected with anacceptable time spreading at very low (e.g., negative) SNRs, allowingfor longer distances between transmitter and receiver.

In one implementation, a sweep in frequency may occur in a secondportion in which an original OFDM symbol of this second portion isshifted by one carrier from one symbol to the next symbol. Anotherpossibility may be to use a predetermined frequency hopping sequence inwhich the original OFDM symbol is shifted by some number of carriers(following a predetermined hopping rule) from one symbol to the next.

Referring now to FIG. 1 , shown is a flow diagram of a method inaccordance with an embodiment. In the high level view shown in FIG. 1 ,method 100 is a method performed by a receiver to receive and process anincoming transmission, more particularly, an OFDM transmission. Asshown, method 100 begins by receiving the OFDM transmission in thereceiver (block 110). Understand that the receiver may receive thistransmission from a transmitter to which it is wirelessly coupled. Forexample, in a given network there may be multiple devices, some or allof which may be capable of both transmission and reception by way ofindependent receiver and transmitter circuitry and/or consolidatedtransceivers.

In any event, in FIG. 1 this OFDM transmission may be received andprocessed in the receiver. Understand that various processing may beperformed, including radio frequency (RF) processing to receive,amplify, filter, etc., and in turn, to downconvert the RF signal to alower frequency (e.g., an intermediate frequency (IF), a low-IF,baseband or so forth). Then in turn, this lower frequency signal isdigitized and various digital processing may be performed afterconversion to the digital signal.

As illustrated in FIG. 1 , this processing may include performing adetection as to the arrival of a valid transmission (block 120). Thisdetection may be based at least in part on detection of a first portionof a preamble of the transmission. As will be described more fullyherein, a preamble of a burst may include multiple portions.

In addition to detection, both coarse and fine frequency estimations maybe performed on this first preamble portion (block 130). As shown inFIG. 1 , irregular comb correlators of the receiver may be used inperforming these frequency estimations to thus determine a carrierfrequency offset. Such information regarding an identified carrierfrequency offset may be used for compensation and other configuring ofthe receiver.

Still referring to FIG. 1 , next at block 140, a coarse timingestimation may be performed on a second preamble portion that has afrequency distortion. More particularly, the irregular comb correlatorsand second correlators of the receiver may be used in this detection.Alternately, the coarse timing may be determined using only the secondcorrelators. Note that this coarse timing thus identifies the start of areceived OFDM symbol within some number of incoming samples (moregenerally as a fraction of the OFDM symbol size).

Still with reference to FIG. 1 , next at block 150, a fine timingestimation may be performed on this second and/or an optional thirdpreamble portion. This fine timing estimation may be used to identifythe received symbol start, with a precision of one incoming sample.Based on the determined information, namely signal detection and thecoarse and fine frequency and timing estimations, at block 160 thereceiver may be configured to receive a data portion of thetransmission. For example, compensations may be configured at variouspoints of the receiver signal processing path to accommodate for anycarrier frequency offset and to ensure that signal processing, includingdemodulation, correctly occurs at the start of a given symbol.Understand while shown at this high level in the embodiment of FIG. 1 ,many variations and alternatives are possible.

Referring now to FIG. 2 , shown is a graphical illustration of apreamble of an OFDM communication in accordance with an embodiment. Asshown in FIG. 2 , preamble 200 includes separate portions, including afirst portion 210, also referred to as a Preamble-Part1, a secondportion 220 referred to as a Preamble-Part2, and an optional thirdportion 230, which may or may not be present in a given implementation.

Note that in FIG. 2 , preamble 200 is shown in graphical illustrationwith the time domain along the x-axis and the frequency domain along they-axis. As shown, first portion 210 may be formed as a simple waveformthat may be used for purposes of signal detection and coarse and finefrequency estimations (namely coarse and fine carrier frequency offsetdeterminations). As illustrated, this first portion includes a pluralityof symbols Pr-10-Pr 1N. Although embodiments are not limited in thisregard, in one particular example, first portion 210 may be formed of 40symbols. Note that in the illustration, each of these symbols mayprovide the same information. Specifically, first portion 210 may beimplemented as having a relatively small number of non-zero carriers 212₀-212 _(x). Since each symbol provides the same information, thesenon-zero carriers are shown as horizontal lines, indicating that eachcarrier includes the same value in each symbol. Also of significance,note that at least some of these carriers 212 have irregular spacing.Stated another way, there is not a constant offset between at least someof these non-zero carriers.

As will be described herein, the irregular spacing between thesecarriers can be used to better identify a correct carrier frequencyoffset, since corresponding correlators in a receiver may have a similarirregular comb structure. Although embodiments are not limited in thisregard, in one example there may be twelve non-zero carriers 212.Further while different numbers of carriers may be provided in differentexamples, there may be 64, 128 or 256 carriers per symbol, as generatedby a fast Fourier transform (FFT) engine (not shown in FIG. 2 ). Moregenerally, there may be N-M non-zero carriers 212 (where N is greaterthan M, N being the total number of carriers in a symbol, and M beingthe number of zero carriers).

Still referring to FIG. 2 , second portion 220 may be formed of adifferent number of symbols Pr-20-Pr 2Y. Although embodiments are notlimited in this regard, in one example there may be thirteen symbols inthis second preamble portion. As shown, each symbol may be frequencydisrupted (having a carrier shift from one symbol to the next), in thatthe active non-zero carriers (214 ₀-214 _(x)) are at different carriers.This frequency disruption portion may be used to perform a coarse timingestimation as will be described further herein (and possibly also forfine timing estimation). Understand that in different implementations,various frequency disruptions, including frequency sweeps, hops, mixesand so forth may be present. Further, while irregular carrier spacing isshown in this example, it is possible for the active non-zero carriers214 to have a regular spacing. Also understand that there need not bethe same number of active non-zero carriers in second portion 220 asthere are in first portion 210.

With further reference to FIG. 2 , a preamble 200 may include anoptional third preamble portion 230 that may be implemented as anotherplurality of symbols Pr-30-Pr-3Z. In one embodiment, each of thesesymbols may be formed as a complete fully known OFDM symbol that can beused for purposes of performing a fine timing estimation (where suchfine timing estimation is not done using second preamble portion 220).Understand while shown at this high level in the embodiment of FIG. 2 ,many variations and alternatives of a preamble in accordance with anembodiment may be possible.

Referring now to FIG. 3 , shown is a block diagram of a transmitter inaccordance with an embodiment. More specifically as shown in FIG. 3 , atransmitter 300, which may be implemented as part of transceivercircuitry of an IoT or other integrated circuit, includes a digitalsignal processor (DSP) 310. In other cases, transmitter 300 may be astandalone transmitter.

In any event, DSP 310 may process information to be communicated in anOFDM transmission. In turn, the message information, e.g., digitalmessage information, is provided to a baseband processor 320. Forpurposes of OFDM communication, this message information may bepackaged, modulated and further processed. Finally, the messageinformation, which may be in the frequency domain as a plurality ofsymbols each having multiple carriers, may be converted to a time domainsignal via an inverse Fourier transform (IFT) engine 340.

Note that prior to transmitting the actual content of a message, first apreamble may be generated and sent. Thus as shown in FIG. 3 , a preamblegeneration circuit 330 may be provided within baseband processor 320. Asshown, preamble generation circuit 330 includes multiple preamblegenerators, including a first preamble generator 332 and a secondpreamble generator 336. Although not shown, understand that additionalpreamble generation circuitry may be present to form additional preambleportions such as an optional third preamble portion.

First preamble generator 332 may be configured to generate a firstportion of a preamble. As shown, first preamble generator 332 includesstorages 333 and 334 that may store information including an activecarrier list and complex modulation values. Note that this informationmay be stored in a memory structure, such as registers, random accessmemory or so forth. In different implementations, this information maybe obtained from a non-volatile storage, e.g., as part of firmware thatis loaded into transmitter 300 during initialization.

In embodiments, the active carrier list may be a list having anidentification of active (non-zero) carriers for this first preambleportion. As discussed above, different numbers of non-zero carriers maybe present. In one example, there may be twelve non-zero carriers.Further as discussed above, these non-zero carriers may have irregularspacing. In addition, these non-zero carriers may be modulated usingcomplex modulation values, as stored in storage 334. By using complexmodulation values that may be of a non-N-ary sequence, this preambleportion may be generated having a minimal PAPR.

Understand in the implementation of FIG. 3 , first preamble generator332 may use the information in storages 333, 334 to generate symbols ofthe first preamble portion that have selected, irregularly spacednon-zero carriers using complex modulation values. In other cases firstpreamble generator 332 may be configured to generate a first preambleportion that has regularly spaced non-zero carriers modulated withcomplex modulation values. Still other variations are possible. Forexample, in yet other implementations another design may be used for thefirst preamble portion such as irregularly spaced non-zero carriermodulated in another manner, such as via a binary sequence.

Referring now to second preamble generator 336, included therein is astorage 337 and a frequency disruption circuit 338. Storage 337 maystore an initial carrier list that identifies which carriers are to beactive for a first symbol of a second preamble portion. Frequencydisruption circuit 338 may be configured to generate the second preambleportion by applying a given carrier shift or other frequency disruptionfrom one symbol to the next during this second preamble portion. In thisway, second preamble generator 336 may generate a first symbol accordingto the initial carrier list stored in storage 337. Then the carriers maybe updated from one symbol to the next according to the configuration offrequency disruption circuit 338. For example, one or more of frequencyshifting or hopping may occur from one symbol to the next during thissecond preamble portion by adjusting active carriers via frequencydisruption circuit 338.

Baseband processor 320 may output OFDM symbols in the time domain, suchthat for a given transmission first a preamble is generated and sent andthen symbols having the message content are sent. As shown, the OFDMtransmission may be converted into an analog signal via adigital-to-analog converter (DAC) 350. This signal may be filtered in afilter 360. Thereafter the signal may be upconverted to an RF level viaa mixer 370, which receives a mixing signal from a clock generator 375.Then the RF signal may be amplified in a power amplifier 380 andtransmitted via an antenna 390. Understand while shown at this highlevel in the embodiment of FIG. 3 , many variations and alternatives arepossible.

Referring now to FIG. 4 , shown is a block diagram of a receiver inaccordance with an embodiment. Receiver 400 may be implemented as partof transceiver circuitry of an IoT or other integrated circuit (and thusmay be implemented in a single IC along with transmitter 300 of FIG. 3 ,in some cases). As shown, receiver 400 may receive incoming RF signalsvia an antenna 410 that in turn is coupled to a low noise amplifier(LNA) 415, which may amplify the signals and provide them to a filter420. Thereafter, the RF signals may be downconverted to lower frequencysignals via a mixer 430 that receives a mixing signal from a clockgenerator 435. The resulting downconverted signals may be digitized inan analog-to-digital converter (ADC) 440, and then provided to abaseband processor 450 for further processing.

Within baseband processor 450, acquisition operations, includingdetection, and carrier frequency offset and timing determinations, maybe performed. Thus as shown, baseband processor 450 includes a signaldetector 452, a CFO circuit 456 and a timing circuit 458. As furthershown, baseband processor 450 includes an FFT engine 454, which may takeincoming time domain signals and convert them to the frequency domain asa stream of symbols each having multiple carriers. In addition, acontrol circuit 455 is present and may, based on one or more of signaldetection, CFO determination and timing determination, control thereceiver configuration to appropriately receive and process an incomingtransmission. Thus as shown, control circuit 455 may, e.g., based on alevel of carrier frequency offset, send a control signal to clockgenerator 435 to update a frequency of the mixing signal. In anotherexample, control circuit 455 may enable digital compensation for CFO bycontrolling baseband processor 450 to perform frequency offsetcompensation. In different implementations, signal detector 452 maydetect presence of an incoming signal based on the incoming time domainsignal or a frequency domain signal output by FFT engine 454.

CFO circuit 456, as shown, includes a first plurality of correlators 457_(0-n). As described above, each correlator 457 may have an irregularcomb structure that is designed to match the irregular carrier spacingof the incoming first preamble portion. Although embodiments are notlimited in this regard, there may be 21 correlators 457 each associatedwith a given carrier frequency offset. Correlators 457 may determinecorrelation results by performing auto-correlations and/orcross-correlations. By providing an irregular comb structure for usewith this first preamble portion, one correlator may fit perfectly forthe targeted comb position, while the other correlators fit poorly, suchthat poor correlation results occur for these other correlators. In anembodiment, a configuration setting (stored in a non-volatile memory)may be used to define the irregular comb structure. As such, theappropriate carrier frequency offset may be readily determined as thereis a large deviation between the matching correlator and the othercorrelators. CFO circuit 456 may provide this CFO determination (bothcoarse and fine) to control circuit 455, for use in performing anyappropriate compensations to compensate for carrier frequency offset.

In turn, timing circuit 458 includes a second plurality of correlators459 _(0-n). Depending on implementation, each correlator 459 may have aregular or irregular comb structure that is designed to match thecarrier spacing of the incoming second preamble portion. Althoughembodiments are not limited in this regard, there may be 20 correlators459 each associated with a given time-phase. In some embodiments, thestart of the second preamble portion may be identified using correlationresults from both correlators 457 and 459. In these embodiments, thebeginning of the second preamble portion can be identified whencorrelation results from correlators 459 exceed correlation results fromcorrelators 457. In another case, second correlation results alone maybe used to identify this second portion start.

Finally with reference to FIG. 4 , incoming message information may besent to a demodulator 460, where demodulation may be performed.Understand while shown at this high level in the embodiment of FIG. 4 ,many variations and alternatives are possible.

As discussed above, a transmitter may generate a first preamble portionhaving irregular carrier spacing between non-zero carriers. And in turn,a receiver may include correlators having an irregular pilot combstructure. Referring now to FIG. 5 , shown is a graphical illustrationof a representative irregular pilot comb of a first preamble portion andcorresponding irregular comb structures of a plurality of correlators ofa receiver. As shown in FIG. 5 , a first preamble portion 510 has alimited set of non-zero carriers 512 ₀-512 ₁₁.

FIG. 5 further show correlation results of sets of correlators 520having different CFO offsets (ranging from zero offset to offsets of+3/−3). As seen in a first example correlation result 530 of a coarsefrequency algorithm a coarse frequency perfect correlation result occursat CFO 0 carrier, which has a perfect correlation level of 12 (in thisexample). In this case, correlation is maximal for Offset 0 and null forother offsets except offset +3(−3), where correlation is medium.

As further shown in FIG. 5 , in a second example correlation result 540of a coarse frequency algorithm, a coarse frequency perfect correlationresult occurs at CFO −1 carrier, which has a perfect correlation levelof 12 (in this example). In this case, correlation is maximal for Offset−1 and null for other offsets except offset +2, where correlation ismedium.

In these 2 cases (perfect correlation), the coarse frequency algorithmdetects that the signal is received with a coarse carrier offset of 0(in first example 530) and −1 (in second example 540). If in theseexamples, if the signal is received with a noise level stronger than thesignal itself (negative SNR), the correlation on offset +3 (+2, insecond example 540) could potentially appear higher than the correlationon offset 0 (−1, in second example 540), which would end with a badcoarse frequency estimation. However, the probability of bad decision onthe coarse frequency algorithm is much lower using an irregular combstructure, thanks to a smaller level of correlation on alternativeoffsets as compared to the optimum offset. In contrast, in conventionalcorrelators leveraging uniform spacing of preamble carriers, alternativeoffsets can result in correlations much closer to an optimalcorrelation, potentially leading to an error in coarse CFOdetermination.

Additional features of a first preamble portion may also enabletransmission optimized for power consumption vs transmission power. Moreparticularly, a sequence used for generating the non-zero carriers canbe carefully selected to realize a reduced PAPR, leading to better powerconsumption vs transmission power. Note that such sequence design can beused in a preamble portion having uniform carrier spacing or non-uniformirregular carrier spacing as described above. And while some embodimentsmay desirably leverage both irregular carrier spacing and a specialsequence design, understand that in other cases they can be usedindependently.

In contrast, conventional preambles such as used in Wi-SUN implement abinary sequence to generate carriers. More specifically, a next sequenceof: [−1, −1, −1, 1, 1, 1, 1, −1, 1, 1, −1, 1] results, which is the BPSKmodulation of the next binary sequence [1, 1, 1, 0, 0, 0, 0, 1, 0, 0, 1,0]. This sequence was not chosen randomly. In fact, it is the 12 bitbinary sequence that, when BPSK modulated on a set of carriers, givesthe smallest PAPR. In the Wi-SUN standard, this PAPR is over 2 dB. InPAPR optimized system, such level can undesirably impact transmitterperformances.

With embodiments, a preamble sequence can be used to result in a smallerPAPR, even if all pilots are maintained with the same gain. Morespecifically in embodiments a sequence of complex numbers may begenerated so that the resulting PAPR of a symbol, when applying thesecomplex numbers on the different selected subcarriers is at a minimumlevel (or at least as small as possible).

These complex numbers can be generated leveraging the understanding thatthe complex-phase portion of these numbers is not necessarily used inreceiver preamble processing. That is, the complex-phase portion is notused to perform any of detection, CFO determination or timingdetermination. As such, the complex-phase portions can be set atarbitrary or random values to optimize a shape of the transmitted signalto realize better PAPR.

In embodiments, the complex values can be defined as a random orarbitrary sequence, where each complex value has a real portion and animaginary portion. These individual real (x) and imaginary (y) portionscan be squared and summed (as x²+y²), where x and y are the randomvalues for the real and imaginary portions, respectively, to result inan absolute value of a sum of squares value for a given complex valuethat substantially equals 1. Of course while in this example, a moduleof 1 is a constraint selected before trying to find a good sequence, inother cases a different module or other constraint can be selected andcomplex-phase values adjusted to result in transmission with a reducedPAPR.

For one example, assume a set of non-zero subcarriers having positions[−24, −20, −16, −12, −8, −4, 4, 8, 12, 16, 20, 24] is used, thefollowing arbitrary complex sequence can be applied as shown in Table 1.

TABLE 1 −0.661480 + I * −0.749963  −0.172436 + I * 0.985021  −0.007412 +I * 0.999973   0.884100 + I * −0.467298 −0.883648 + I * −0.4681510.932095 + I * 0.362214  −0.607242 + I * 0.794517  −0.427617 + I *−0.903960 0.541015 + I * −0.841013 0.993106 + I * −0.117219  0.332095 +I * −0.943246  0.982724 + I * −0.185078]

Looking at the first complex number (−0.661480+I*−0.749963), whenindividual components are squared and summed, a sum of squares ofsubstantially 1 (approximately 0.998) results. For the above example, a64 carrier OFDM symbol can be generated with a PAPR of substantially1.23 dB.

Of course, while specific numbers are illustrated above for one example,understand that many other combinations of arbitrary complex numbers canbe used in other embodiments. Further, these numbers need not have theprecision (6 places) shown above, and can be selected with greater orsmaller precision in other cases.

According to the Wi-SUN specification, its preamble has a complex-phasedisruption at the end. This inverse complex-phase section is used forcoarse timing. However, such a complex-phase disruption gives goodsynchronization only for positive SNRs (or down to −2 −3 dB).

In embodiments, to enable receivers to receive and successfully processweaker signals, a second preamble portion may be used that has awaveform having a frequency disruption rather than a complex-phasedisruption. In example embodiments, this preamble portion may have awaveform that is based on a known pattern of OFDM subcarrier modulation.In one example, the disruption is based on a frequency jump from oneOFDM symbol to the next. By doing so, if a coarse and fine frequencyalgorithm have converged during the first step, a coarse time algorithmwill recover information from the whole time/frequency plane. In somecases, there may be a modulation from symbol to symbol on this frequencydisruption part.

Different scenarios are possible for this waveform. In oneimplementation, a frequency step is regular (from 1 symbol to the next),also referred to as a frequency sweep scenario.

As shown in FIG. 6 , a preamble 600 (which may be a transition sectionof preamble between preamble portions) includes a first portion 610having a plurality of symbols (in the time domain) followed by a secondportion 620 also having a plurality of symbols. In this example, infirst portion 610, each non-zero carrier (in the frequency domain) hasthe same value (shown generically as a 1 or −1 value; of coursedifferent values, including complex values may be used to modulate thesecarriers). And in first portion 610, the non-zero carriers are static inthat they do not change from symbol to symbol. Then second portion 620(having similarly generic 1 or −1 values so as to not obscure thefrequency disruption aspect; however understand that there maysymbol-to-symbol modulation in second portion 620) provides a frequencydisruption by way of a sweep of one carrier from one symbol to another.Of course in other examples, the frequency sweep between symbols may bemore than a single carrier, and can proceed in a positive or negativedirection.

In another scenario a frequency step is not regular (from one symbol tothe next), also referred to as a frequency hop scenario. As shown inFIG. 7 , a preamble 700 (which may be a transition section of preamblebetween preamble portions) includes a first portion 710 followed by asecond portion 720. In this example, in first portion 710, each non-zerocarrier has the same static value and second portion 720 provides adifferent frequency disruption by way of hopping carriers from onesymbol to another. As shown in FIG. 7 , which is one example of afrequency hop scenario, there is a positive jump of 3 carriers, then anegative jump of 2 carriers, followed by a positive jump of 1 carrier,in turn followed by a negative jump of 2 carriers. This sequence maycontinue for a remainder of second preamble 720, or a hop sequence caninclude additional jumps before proceeding again through the sequence.Of course in other examples, the frequency hop between symbols can vary.

In yet another scenario, a frequency step is regular (from one symbol tothe next), with a hop at first, also referred to as a frequency mixscenario. As shown in FIG. 8 , a preamble 800 (which may be a transitionsection of preamble between preamble portions) includes a first portion810 followed by a second portion 820. In this example, in first portion810, each non-zero carrier has the same static value and second portion820 provides a different frequency disruption by way of a frequency mix.As shown in this example, there is an initial hop of two carriers (inthe positive frequency direction) from the last symbol of first portion810 to the first symbol of second portion 820. And then a frequencysweep of one carrier (in the negative frequency direction) proceeds fromone symbol to the next. Of course, other examples are possible. Forexample, a frequency mix scenario may first take the form of a frequencysweep followed by a frequency hop. Or combinations of multiple sweepsand hops may occur.

Note that a frequency disruption sequence can be different than thesequence used for a first preamble portion. Referring now to FIG. 9 , apreamble 900 (which may be a transition section of preamble betweenpreamble portions) includes a first portion 910 followed by a secondportion 920. In this example, in first portion 910, each non-zerocarrier has the same static value and second portion 920 provides adifferent frequency disruption by way of a frequency sweep. Note in thisexample, there are different numbers of non-zero carriers in the twopreamble portions, and thus second preamble 920 does not use the samesequence as first preamble 910. While this example shows a frequencysweep case, hops and mix scenarios may similarly leverage differentsequences for different preamble portions. Moreover, in this example,the number of active carriers being different in portion 910 and 920, anadjustment gain could be applied to each symbol to adjust the averagepower.

In yet another implementation, a disruption zone can be a continuoussequence that uses contiguous carriers. This disruption portion may bebased on a known OFDM symbol that is frequency shifted from one symbolto the next with a known hopping sequence, regardless of the previouspart of the preamble.

Referring now to FIG. 10 , shown is a frequency mix scenario with ashift sequence having continuous carriers for disruption. As shown inFIG. 10 , a preamble 1000 (which may be a transition section of preamblebetween preamble portions) includes a first portion 1010 followed by asecond portion 1020. In this example, in first portion 1010, eachnon-zero carrier has the same static value and second portion 1020provides a frequency disruption first with a frequency hop followed by afrequency sweep. And note the presence of contiguous carriers. Thus itis possible for a frequency disruption to not necessarily be linked to acomb of active carriers, but can even be used with a continuously activecarriers symbol. Different scenarios of course may be used in otherexamples. In this example again, the number of active carriers beingdifferent in portion 1010 and 1020, an adjustment gain could be apply toeach symbol to adjust the average power.

Referring now to FIG. 11 , shown is a block diagram of a representativeintegrated circuit 1100 that includes transceiver circuitry as describedherein. In the embodiment shown in FIG. 11 , integrated circuit 1100 maybe, e.g., a microcontroller, wireless transceiver that may operateaccording to one or more wireless protocols (e.g., WLAN-OFDM, WLAN-DSSS,Bluetooth, among others), or other device that can be used in a varietyof use cases, including sensing, metering, monitoring, embeddedapplications, communications, applications and so forth, and which maybe particularly adapted for use in an IoT device.

In the embodiment shown, integrated circuit 1100 includes a memorysystem 1110 which in an embodiment may include a non-volatile memorysuch as a flash memory and volatile storage, such as RAM. In anembodiment, this non-volatile memory may be implemented as anon-transitory storage medium that can store instructions and data. Suchnon-volatile memory may store instructions, including instructions forgenerating and processing preambles and data for generating thepreambles having particular irregular comb structures and/or usingnon-N-ary complex values and/or frequency distortions described herein.

Memory system 1110 couples via a bus 1150 to a digital core 1120, whichmay include one or more cores and/or microcontrollers that act as a mainprocessing unit of the integrated circuit. In turn, digital core 1120may couple to clock generators 1130 which may provide one or more phaselocked loops or other clock generator circuitry to generate variousclocks for use by circuitry of the IC.

As further illustrated, IC 1100 further includes power circuitry 1140,which may include one or more voltage regulators. Additional circuitrymay optionally be present depending on particular implementation toprovide various functionality and interaction with external devices.Such circuitry may include interface circuitry 1160 which may provideinterface with various off-chip devices, sensor circuitry 1170 which mayinclude various on-chip sensors including digital and analog sensors tosense desired signals, such as for a metering application or so forth.

In addition as shown in FIG. 11 , transceiver circuitry 1180 may beprovided to enable transmission and receipt of wireless signals, e.g.,according to one or more of a local area or wide area wirelesscommunication scheme, such as Zigbee, Bluetooth, IEEE 802.11, IEEE802.15.4, cellular communication or so forth. As shown, transceivercircuitry 1180 includes a PA 1185 that may transmit OFDM signals havinglow PAPR as described herein. Understand while shown with this highlevel view, many variations and alternatives are possible.

Note that ICs such as described herein may be implemented in a varietyof different devices such as an IoT device. This IoT device may be, astwo examples, a smart bulb of a home or industrial automation network ora smart utility meter for use in a smart utility network, e.g., a meshnetwork in which communication is according to an IEEE 802.15.4specification or other such wireless protocol.

Referring now to FIG. 12 , shown is a high level diagram of a network inaccordance with an embodiment. As shown in FIG. 12 , a network 1200includes a variety of devices, including smart devices such as IoTdevices, routers and remote service providers. In the embodiment of FIG.12 , a mesh network 1205 may be present in a location having multipleIoT devices 1210 _(0-n). Such IoT devices may generate and processpreambles of OFDM packets as described herein. As shown, at least oneIoT device 1210 couples to a router 1230 that in turn communicates witha remote service provider 1260 via a wide area network 1250, e.g., theinternet. In an embodiment, remote service provider 1260 may be abackend server of a utility that handles communication with IoT devices1210. Understand while shown at this high level in the embodiment ofFIG. 12 , many variations and alternatives are possible.

While the present disclosure has been described with respect to alimited number of implementations, those skilled in the art, having thebenefit of this disclosure, will appreciate numerous modifications andvariations therefrom. It is intended that the appended claims cover allsuch modifications and variations.

What is claimed is:
 1. A receiver comprising: a low noise amplifier(LNA) to receive and amplify a radio frequency (RF) signal comprising apacket; a mixer coupled to the LNA to downconvert the RF signal to asecond frequency signal; a digitizer coupled to the mixer to digitizethe second frequency signal to a digital signal; and a baseband circuitcoupled to the digitizer to process the digital signal, the basebandcircuit comprising: a first plurality of correlators having an irregularcomb structure, each of the first plurality of correlators associatedwith a carrier frequency offset and to calculate a first correlation ona first portion of a preamble of the packet.
 2. The receiver of claim 1,wherein the irregular comb structure is configured to match an irregularcarrier spacing of the first portion of the preamble of the packet. 3.The receiver of claim 2, wherein the first plurality of correlators areto calculate the first correlation comprising at least one of anauto-correlation or a cross-correlation.
 4. The receiver of claim 1,wherein each of the first plurality of correlators is associated withone of a plurality of carrier frequency offsets.
 5. The receiver ofclaim 4, further comprising a carrier frequency offset circuit todetermine the carrier frequency offset based on a first correlationcalculated by each of the first plurality of correlators.
 6. Thereceiver of claim 5, wherein the carrier frequency offset circuit is todetermine the carrier frequency offset based on the first correlationcalculated by each of the first plurality of correlators having amaximal value.
 7. The receiver of claim 1, wherein the baseband circuitfurther comprises a second plurality of correlators, each of the secondplurality of correlators associated with a time-phase and to calculate asecond correlation on a second portion of the preamble of the packet,the second portion of the preamble of the packet having at least onefrequency disruption.
 8. The receiver of claim 1, wherein the receiveris to receive the first portion of the preamble of the packet having afirst plurality of symbols, each of the first plurality of symbolshaving a plurality of carriers, wherein a first subset of the pluralityof carriers have non-zero values.
 9. The receiver of claim 8, whereinthe receiver is to receive the plurality of carriers comprising Ncarriers, wherein N-M of the N carriers are the first subset having thenon-zero values and an irregular carrier spacing, wherein N is a numberof the plurality of carriers and M is a number of the plurality ofcarriers having a zero value, N greater than M, wherein the irregularcomb structure corresponds to the irregular carrier spacing.
 10. Thereceiver of claim 8, further comprising a fast Fourier transform (FFT)engine to receive the packet and to output the first plurality ofsymbols each having the plurality of carriers in a frequency domain. 11.The receiver of claim 1, further comprising a non-volatile memory tostore a first configuration setting to define the irregular combstructure of the first plurality of correlators.
 12. A non-transitorystorage medium comprising instructions that when executed cause areceiver to perform a method comprising: receiving a packet in thereceiver; and performing a frequency estimation on a first preambleportion of the packet using a first plurality of correlators of thereceiver, the first preamble portion formed of a plurality of symbols,each of the plurality of symbols having N-M non-zero carriers, whereinat least some of the N-M non-zero carriers are irregularly spaced,wherein N is a number of carriers in a symbol and M is a number of thecarriers in the symbol having a zero value, N greater than M.
 13. Thenon-transitory storage medium of claim 12, further comprisinginstructions that when executed cause the receiver to perform the methodfurther comprising performing a coarse frequency estimation on the firstpreamble portion using the first plurality of correlators.
 14. Thenon-transitory storage medium of claim 13, further comprisinginstructions that when executed cause the receiver to perform the methodfurther comprising performing a fine frequency estimation on the firstpreamble portion based on the coarse frequency estimation and using theplurality of first correlators.
 15. The non-transitory storage medium ofclaim 14, further comprising configuring the receiver for receipt of adata portion of the packet based at least in part on the fine frequencyestimation.
 16. The non-transitory storage medium of claim 13, furthercomprising instructions that when executed cause the receiver to performthe method further comprising performing a timing estimation on a secondpreamble portion of the packet using a second plurality of correlatorsof the receiver.
 17. The non-transitory storage medium of claim 12,further comprising instructions that when executed cause the receiver toperform the method further comprising configuring the first plurality ofcorrelators to have an irregular comb structure using configurationinformation stored in a non-volatile storage.
 18. A system comprising:an antenna to receive and transmit a radio frequency (RF) signal; and anintegrated circuit coupled to the antenna, the integrated circuitcomprising: a transmitter to transmit a packet in the RF signal, thetransmitter comprising a preamble generation circuit to generate a firstportion of a preamble of the packet having a first plurality of symbols,each of the first plurality of symbols having a plurality of carriers,wherein a first subset of the plurality of carriers have non-zerovalues, at least some of the first subset of the plurality of carriershaving irregular carrier spacing.
 19. The system of claim 18, whereinthe integrated circuit further comprises a first storage to store anidentification of the at least some of the first subset of the pluralityof carriers having the non-zero values.
 20. The system of claim 19,wherein the transmitter is to transmit the first portion of the preamblehaving the irregular carrier spacing to correspond to an irregular combstructure of a plurality of correlators of a receiver to receive thepacket.